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general description the MAX12527 is a dual 3.3v, 12-bit analog-to-digital converter (adc) featuring fully differential wideband track-and-hold (t/h) inputs, driving internal quantizers. the MAX12527 is optimized for low power, small size, and high dynamic performance in intermediate frequen- cy (if) and baseband sampling applications. this dual adc operates from a single 3.3v supply, consuming only 620mw while delivering a typical 69.8db signal-to- noise ratio (snr) performance at a 175mhz input fre- quency. the t/h input stages accept single-ended or differential inputs up to 400mhz. in addition to low oper- ating power, the MAX12527 features a 166? power- down mode to conserve power during idle periods. a flexible reference structure allows the MAX12527 to use the internal 2.048v bandgap reference or accept an externally applied reference and allows the refer- ence to be shared between the two adcs. the refer- ence structure allows the full-scale analog input range to be adjusted from ?.35v to ?.15v. the MAX12527 provides a common-mode reference to simplify design and reduce external component count in differential analog input circuits. the MAX12527 supports either a single-ended or differ- ential input clock. user-selectable divide-by-two (div2) and divide-by-four (div4) modes allow for design flexibil- ity and help eliminate the negative effects of clock jitter. wide variations in the clock duty cycle are compensated with the adc? internal duty-cycle equalizer (dce). the MAX12527 features two parallel, 12-bit-wide, cmos-compatible outputs. the digital output format is pin-selectable to be either two? complement or gray code. a separate power-supply input for the digital out- puts accepts a 1.7v to 3.6v voltage for flexible interfac- ing with various logic levels. the MAX12527 is available in a 10mm x 10mm x 0.8mm, 68-pin thin qfn package with exposed paddle (ep), and is specified for the extended (-40 c to +85 c) temperature range. for a 14-bit, pin-compatible version of this adc, refer to the max12557 data sheet. applications if and baseband communication receivers cellular, lmds, point-to-point microwave, mmds, hfc, wlan i/q receivers ultrasound and medical imaging portable instrumentation digital set-top boxes low-power data acquisition features ? direct if sampling up to 400mhz ? excellent dynamic performance 70.4db/69.8db snr at f in = 70mhz/175mhz 84.4dbc/80.2dbc sfdr at f in = 70mhz/175mhz ? 3.3v low power operation 647mw (differential clock mode) 620mw (single-ended clock mode) ? fully differential or single-ended analog input ? adjustable differential analog input voltage ? 750mhz input bandwidth ? adjustable, internal or external, shared reference ? differential or single-ended clock ? accepts 25% to 75% clock duty cycle ? user-selectable div2 and div4 clock modes ? power-down mode ? cmos outputs in two? complement or gray code ? out-of-range and data-valid indicators ? small, 68-pin thin qfn package ? 14-bit compatible version available (max12557) ? evaluation kit available (order MAX12527 ev kit) MAX12527 dual, 65msps, 12-bit, if/baseband adc ________________________________________________________________ maxim integrated products 1 ordering information 19-3543; rev 0; 2/05 for pricing, delivery, and ordering information, please contact maxim/dallas direct! at 1-888-629-4642, or visit maxim? website at www.maxim-ic.com. evaluation kit available part temp range pin-package MAX12527etk -40 c to +85 c 68 thin qfn-ep* (10mm x 10mm x 0.8mm) pin configuration appears at end of data sheet. * ep = exposed paddle. part sampling rate ( msps) resolution (bits) max12557 65 14 MAX12527 65 12 selector guide
MAX12527 dual, 65msps, 12-bit, if/baseband adc 2 _______________________________________________________________________________________ absolute maximum ratings electrical characteristics (v dd = 3.3v, ov dd = 2.0v, gnd = 0, refin = refout (internal reference), c l 10pf at digital outputs, v in = -0.5dbfs (differen- tial), diffclk/ seclk se t clk t c c t t c s t e clk clk e et e e c e e c clk seclk t se c t c t c c t c c t c s t c c l t c ete sl cts t ts c ccc l ls l ls e s e s l t c e c c c sle s ces te c clk c l c c c cctestcs ss ss s s s s s s s s
MAX12527 dual, 65msps, 12-bit, if/baseband adc _______________________________________________________________________________________ 3 electrical characteristics (continued) (v dd = 3.3v, ov dd = 2.0v, gnd = 0, refin = refout (internal reference), c l 10pf at digital outputs, v in = -0.5dbfs (differen- tial), diffclk/ seclk se t clk t c c t t c ete sl cts t ts s s s s s s s s s s s s s s s t t s s s s s s s s s t s s s tt tt s s s s s s s s tt s s tt s s s s t c c ls s
MAX12527 dual, 65msps, 12-bit, if/baseband adc 4 _______________________________________________________________________________________ electrical characteristics (continued) (v dd = 3.3v, ov dd = 2.0v, gnd = 0, refin = refout (internal reference), c l 10pf at digital outputs, v in = -0.5dbfs (differen- tial), diffclk/ seclk se t clk t c c t t c ete sl cts t ts t c tecel cctestcs s c s s tel eeece et et et et l et et t c tc e c s et sc c s ee eeece e e et e e c e e c e e e e c c c e e e e e e e e e e e e e e e e t c tc e c ee etel eeece e e e c e e c c c e e e e c e e e e c c c e e e e e e
MAX12527 dual, 65msps, 12-bit, if/baseband adc _______________________________________________________________________________________ 5 electrical characteristics (continued) (v dd = 3.3v, ov dd = 2.0v, gnd = 0, refin = refout (internal reference), c l 10pf at digital outputs, v in = -0.5dbfs (differen- tial), diffclk/ seclk se t clk t c c t t c ete sl cts t ts e s c e e e e s c e e e c s c c c c e e c c e c e c c c c clck ts clk clk se t clk seclk clk se l t l clk seclk clk c s clk seclk c clk seclk clk clk e clk c c clk e tl ts clk seclk t t lt l lc c c tltts sk l l sk sce sce tslc lek
MAX12527 dual, 65msps, 12-bit, if/baseband adc 6 _______________________________________________________________________________________ electrical characteristics (continued) (v dd = 3.3v, ov dd = 2.0v, gnd = 0, refin = refout (internal reference), c l 10pf at digital outputs, v in = -0.5dbfs (differen- tial), diffclk/ seclk se t clk t c c t t c ete sl cts t ts t s c c t ts c c e eeets s s s clk seclk s clk seclk s c s clk seclk s clk seclk s s c
MAX12527 dual, 65msps, 12-bit, if/baseband adc _______________________________________________________________________________________ 7 electrical characteristics (continued) (v dd = 3.3v, ov dd = 2.0v, gnd = 0, refin = refout (internal reference), c l 10pf at digital outputs, v in = -0.5dbfs (differen- tial), diffclk/ seclk se t clk t c c t t c ete sl cts t ts t cctestcs c c c l cl s t e set t e l t ke e s c c s c t t c e et c l s clk seclk t clk t c fft plot (16,384-point data record) MAX12527 toc01 analog input frequency (mhz) amplitude (dbfs) 30 25 20 15 10 5 -100 -80 -60 -40 -20 0 -120 035 f clk = 65mhz f in = 3.00125mhz a in = -0.53dbfs snr = 71db sinad = 70.9db thd = -94dbc sfdr = 93.6dbc hd2 hd3 fft plot (32,768-point data record) MAX12527 toc02 analog input frequency (mhz) amplitude (dbfs) 30 25 15 20 10 5 -110 -100 -90 -80 -70 -60 -50 -40 -30 -20 -10 0 -120 0 f clk = 65.00352mhz f in = 32.40059mhz a in = -0.506dbfs snr = 70.5db sinad = 70.2db thd = -86.9dbc sfdr = 88.7dbc hd2 hd3 fft plot (32,768-point data record) MAX12527 toc03 analog input frequency (mhz) amplitude (dbfs) 30 25 15 20 10 5 -110 -100 -90 -80 -70 -60 -50 -40 -30 -20 -10 0 -120 0 f clk = 65.00352mhz f in = 70.00852mhz a in = -0.506dbfs snr = 70.1db sinad = 69.8db thd = -82.1dbc sfdr = 82.4dbc hd2 hd3
MAX12527 dual, 65msps, 12-bit, if/baseband adc 8 _______________________________________________________________________________________ integral nonlinearity vs. digital output code MAX12527 toc07 digital output code inl (lsb) 3600 3000 1800 2400 1200 600 -0.4 -0.3 -0.2 -0.1 0 0.1 0.2 0.3 0.4 0.5 -0.5 0 4200 f clk = 65mhz f in = 3.00119mhz differential nonlinearity vs. digital output code MAX12527 toc08 digital output code dnl (lsb) 3600 3000 1800 2400 1200 600 -0.4 -0.3 -0.2 -0.1 0 0.1 0.2 0.3 0.4 0.5 -0.5 0 4200 f clk = 65mhz f in = 3.00119mhz snr, sinad vs. analog input frequency (f clk = 65.00352mhz, a in = -0.5dbfs) MAX12527 toc09 f in (mhz) snr, sinad (db) 350 300 200 250 100 150 50 52 54 56 58 60 62 64 66 68 70 72 50 0 400 sinad snr -thd, sfdr vs. analog input frequency (f clk = 65.00352mhz, a in = -0.5dbfs) MAX12527 toc10 f in (mhz) -thd, sfdr (dbc) 350 300 200 250 100 150 50 55 60 65 70 75 80 85 90 95 50 0 400 sfdr -thd snr, sinad vs. analog input amplitude (f clk = 65.00352mhz, f in = 70mhz) MAX12527 toc11 a in (dbfs) snr, sinad (db) -5 -10 -15 -20 -25 -30 -35 -40 -45 -50 25 35 45 55 65 75 15 -55 0 snr sinad -thd, sfdr vs. analog input amplitude (f clk = 65.00352mhz, f in = 70mhz) MAX12527 toc12 a in (dbfs) -thd, sfdr (dbc) -5 -10 -15 -20 -25 -30 -35 -40 -45 -50 35 45 55 65 75 85 95 25 -55 0 sfdr -thd fft plot (32,768-point data record) MAX12527 toc04 analog input frequency (mhz) amplitude (dbfs) 30 25 15 20 10 5 -110 -100 -90 -80 -70 -60 -50 -40 -30 -20 -10 0 -120 0 f clk = 65.00352mhz f in = 174.90525mhz a in = -0.448dbfs snr = 69.4db sinad = 68.9db thd = -78.6dbc sfdr = 81.1dbc hd2 hd3 two-tone imd plot (16,384-point data record) MAX12527 toc05 analog input frequency (mhz) amplitude (dbfs) 30 25 20 15 10 5 -100 -80 -60 -40 -20 0 -120 0 f clk = 65.00352mhz f in1 = 68.49889mhz f in2 = 71.49832mhz a in1 = -6.96dbfs a in2 = -7.02dbfs im3 = -92.25dbc imd = -89.08dbc f in1 f in2 2f in2 + f in1 two-tone imd plot (16,384-point data record) MAX12527 toc06 analog input frequency (mhz) amplitude (dbfs) 30 25 20 15 10 5 -100 -80 -60 -40 -20 0 -120 0 f clk = 65.00352mhz f in1 = 172.50293mhz a in1 = -6.99dbfs f in2 = 177.40198mhz a in2 = -7.01dbfs im3 = -88.88dbc imd = -82.24dbc f in1 f in2 f in1 + f in2 f in2 - f in1 t ypical operating characteristics (continued) (v dd = 3.3v, ov dd = 2.0v, gnd = 0, refin = refout (internal reference mode), c l 5pf at digital outputs, v in = -0.5dbfs, diffclk/ seclk t clk t c
MAX12527 dual, 65msps, 12-bit, if/baseband adc _______________________________________________________________________________________ 9 snr, sinad vs. analog input amplitude (f clk = 65.00352mhz, f in = 175mhz) MAX12527 toc13 a in (dbfs) snr, sinad (db) -5 -10 -15 -20 -25 -30 -35 -40 -45 -50 25 35 45 55 65 75 15 -55 0 snr sinad -thd, sfdr vs. analog input amplitude (f clk = 65.00352mhz, f in = 175mhz) MAX12527 toc14 a in (dbfs) -thd, sfdr (dbc) -5 -10 -15 -20 -25 -30 -35 -40 -45 -50 35 45 55 65 75 85 95 25 -55 0 sfdr -thd snr, sinad vs. clock speed (f in = 70mhz, a in = -0.5dbfs) MAX12527 toc15 f clk (mhz) snr, sinad (db) 60 55 50 45 40 35 30 25 62 64 66 68 70 72 60 20 65 snr sinad -thd, sfdr vs. clock speed (f in = 70mhz, a in = -0.5dbfs) MAX12527 toc16 f clk (mhz) -thd, sfdr (dbc) 60 55 50 45 40 35 30 25 65 70 75 80 85 90 60 20 65 sfdr -thd snr, sinad vs. clock speed (f in = 175mhz, a in = -0.5dbfs) MAX12527 toc17 f clk (mhz) snr, sinad (db) 60 55 50 45 40 35 30 25 62 64 66 68 70 72 60 20 65 snr sinad -thd, sfdr vs. clock speed (f in = 175mhz, a in = -0.5dbfs) MAX12527 toc18 f clk (mhz) -thd, sfdr (dbc) 60 55 50 45 40 35 30 25 65 70 75 80 85 90 60 20 65 sfdr -thd snr, sinad vs. analog supply voltage (f clk = 65.00352mhz, f in = 70mhz) MAX12527 toc19 v dd (v) snr, sinad (db) 3.5 3.4 3.3 3.2 3.1 62 64 66 68 70 72 60 3.0 3.6 sinad snr -thd, sfdr vs. analog supply voltage (f clk = 65.00352mhz, f in = 70mhz) MAX12527 toc20 v dd (v) -thd, sfdr (dbc) 3.5 3.4 3.3 3.2 3.1 65 70 75 80 85 90 60 3.0 3.6 -thd sfdr snr, sinad vs. analog supply voltage (f clk = 65.00352mhz, f in = 175mhz) MAX12527 toc21 v dd (v) snr, sinad (db) 3.5 3.4 3.3 3.2 3.1 62 64 66 68 70 72 60 3.0 3.6 sinad snr t ypical operating characteristics (continued) (v dd = 3.3v, ov dd = 2.0v, gnd = 0, refin = refout (internal reference mode), c l 5pf at digital outputs, v in = -0.5dbfs, diffclk/ seclk t clk t c
MAX12527 dual, 65msps, 12-bit, if/baseband adc 10 ______________________________________________________________________________________ -thd, sfdr vs. analog supply voltage (f clk = 65.00352mhz, f in = 175mhz) MAX12527 toc22 v dd (v) -thd, sfdr (dbc) 3.5 3.4 3.3 3.2 3.1 65 70 75 80 85 90 60 3.0 3.6 -thd sfdr snr, sinad vs. digital supply voltage (f clk = 65.00352mhz, f in = 70mhz) MAX12527 toc23 ov dd (v) snr, sinad (db) 3.3 3.0 2.7 2.4 2.1 1.8 62 64 66 68 70 72 60 1.5 3.6 snr sinad -thd, sfdr vs. digital supply voltage (f clk = 65.00352mhz, f in = 70mhz) MAX12527 toc24 ov dd (v) -thd, sfdr (dbc) 3.3 3.0 2.7 2.4 2.1 1.8 65 70 75 80 85 90 60 1.5 3.6 -thd sfdr snr, sinad vs. digital supply voltage (f clk = 65.00352mhz, f in = 175mhz) MAX12527 toc25 ov dd (v) snr, sinad (db) 3.3 3.0 2.7 2.4 2.1 1.8 62 64 66 68 70 72 60 1.5 3.6 snr sinad -thd, sfdr vs. digital supply voltage (f clk = 65.00352mhz, f in = 175mhz) MAX12527 toc26 ov dd (v) -thd, sfdr (dbc) 3.3 3.0 2.7 2.4 2.1 1.8 65 70 75 80 85 90 60 1.5 3.6 -thd sfdr p diss , i vdd (analog) vs. analog supply voltage (f clk = 65.00352mhz, f in = 175mhz) MAX12527 toc27 v dd (v) p diss , i vdd (mw, ma) 3.5 3.4 3.3 3.2 3.1 100 200 300 400 500 600 700 800 900 0 3.0 3.6 p diss (analog) i vdd p diss , i ovdd (digital) vs. digital supply voltage (f clk = 65.00352mhz, f in = 175mhz) MAX12527 toc28 ov dd (v) p diss , i ovdd (mw, ma) 3.3 3.0 1.8 2.1 2.4 2.7 10 20 30 40 50 60 70 80 0 1.5 3.6 p diss (digital) c l 5pf i ovdd snr, sinad vs. clock duty cycle (f in = 70mhz, a in = -0.5dbfs) MAX12527 toc29 clock duty cycle (%) snr, sinad (db) 65 55 45 35 62 64 66 68 70 72 60 25 75 snr sinad single-ended clock input drive -thd, sfdr vs. clock duty cycle (f in = 70mhz, a in = -0.5dbfs) MAX12527 toc30 clock duty cycle (%) -thd, sfdr (dbc) 65 55 45 35 65 70 75 80 85 90 60 25 75 -thd sfdr single-ended clock input drive t ypical operating characteristics (continued) (v dd = 3.3v, ov dd = 2.0v, gnd = 0, refin = refout (internal reference mode), c l 5pf at digital outputs, v in = -0.5dbfs, diffclk/ seclk t clk t c
MAX12527 dual, 65msps, 12-bit, if/baseband adc ______________________________________________________________________________________ 11 snr, sinad vs. temperature (f in = 175mhz, a in = -0.5dbfs) MAX12527 toc31 temperature ( c) snr, sinad (db) 60 35 10 -15 62 64 66 68 70 72 60 -40 85 snr sinad -thd, sfdr vs. temperature (f in = 175mhz, a in = -0.5dbfs) MAX12527 toc32 temperature ( c) -thd, sfdr (dbc) 60 35 10 -15 65 70 75 80 85 90 60 -40 85 -thd sfdr gain error vs. temperature MAX12527 toc33 temperature ( c) gain error (%fsr) 60 35 10 -15 -2 -1 0 1 2 3 -3 -40 85 offset error vs. temperature MAX12527 toc34 temperature ( c) offset error (% fsr) 60 35 -15 10 -0.2 -0.1 0 0.1 0.2 0.3 -0.3 -40 85 t ypical operating characteristics (continued) (v dd = 3.3v, ov dd = 2.0v, gnd = 0, refin = refout (internal reference mode), c l 5pf at digital outputs, v in = -0.5dbfs, diffclk/ seclk t clk t c
MAX12527 dual, 65msps, 12-bit, if/baseband adc 12 ______________________________________________________________________________________ pin name function 1, 4, 5, 9, 13, 14, 17 gnd converter ground. connect all ground pins and the exposed paddle (ep) together. 2 inap channel a positive analog input 3 inan channel a negative analog input 6 coma channel a common-mode voltage i/o. bypass coma to gnd with a 0.1f capacitor. 7 refap channel a positive reference i/o. channel a conversion range is 2/3 x (v refap - v refan ). bypass refap with a 0.1f capacitor to gnd. connect a 10f and a 1f bypass capacitor between refap and refan. place the 1f refap-to-refan capacitor as close to the device as possible on the same side of the pc board. 8 refan channel a negative reference i/o. channel a conversion range is 2/3 x (v refap - v refan ). bypass refan with a 0.1f capacitor to gnd. connect a 10f and a 1f bypass capacitor between refap and refan. place the 1f refap-to-refan capacitor as close to the device as possible on the same side of the pc board. 10 refbn channel b negative reference i/o. channel b conversion range is 2/3 x (v refbp - v refbn ). bypass refbn with a 0.1f capacitor to gnd. connect a 10f and a 1f bypass capacitor between refbp and refbn. place the 1f refbp-to-refbn capacitor as close to the device as possible on the same side of the pc board. 11 refbp channel b positive reference i/o. channel b conversion range is 2/3 x (v refbp - v refbn ). bypass refbp with a 0.1f capacitor to gnd. connect a 10f and a 1f bypass capacitor between refbp and refbn. place the 1f refbp-to-refbn capacitor as close to the device as possible on the same side of the pc board. 12 comb channel a common-mode voltage i/o. bypass comb to gnd with a 0.1f capacitor. 15 inbn channel b negative analog input 16 inbp channel b positive analog input 18 diffclk/ seclk se c t clk seclk s clk seclk s clk c clk seclk clk clk clk seclk clk clk clk c clk seclk clk clk clk seclk clk clk t c c s t c c s t c c c c c
MAX12527 dual, 65msps, 12-bit, if/baseband adc ______________________________________________________________________________________ 13 pin name function 30 d0b channel b cmos digital output, bit 0 (lsb) 31 d1b channel b cmos digital output, bit 1 32 d2b channel b cmos digital output, bit 2 33 d3b channel b cmos digital output, bit 3 34 d4b channel b cmos digital output, bit 4 35 d5b channel b cmos digital output, bit 5 36 d6b channel b cmos digital output, bit 6 37 d7b channel b cmos digital output, bit 7 38 d8b channel b cmos digital output, bit 8 39 d9b channel b cmos digital output, bit 9 40 d10b channel b cmos digital output, bit 10 41 d11b channel b cmos digital output, bit 11 (msb) 42 dorb channel b data out-of-range indicator. the dorb digital output indicates when the channel b analog input voltage is out of range. dorb = 1: digital outputs exceed full-scale range. dorb = 0: digital outputs are within full-scale range. 44 dav data-valid digital output. the rising edge of dav indicates that data is present on the digital outputs. the MAX12527 evaluation kit (max12557 ev kit) utilizes dav to latch data into any external back-end digital logic. 47 d0a channel a cmos digital output, bit 0 (lsb) 48 d1a channel a cmos digital output, bit 1 49 d2a channel a cmos digital output, bit 2 50 d3a channel a cmos digital output, bit 3 51 d4a channel a cmos digital output, bit 4 52 d5a channel a cmos digital output, bit 5 53 d6a channel a cmos digital output, bit 6 54 d7a channel a cmos digital output, bit 7 55 d8a channel a cmos digital output, bit 8 56 d9a channel a cmos digital output, bit 9 57 d10a channel a cmos digital output, bit 10 58 d11a channel a cmos digital output, bit 11 (msb) 59 dora channel a data out-of-range indicator. the dora digital output indicates when the channel a analog input voltage is out of range. dora = 1: digital outputs exceed full-scale range. dora = 0: digital outputs are within full-scale range. 64 g/ t s t t t c c
MAX12527 detailed description the MAX12527 uses a 10-stage, fully differential, pipelined architecture (figure 1) that allows for high- speed conversion while minimizing power consump- tion. samples taken at the inputs move progressively through the pipeline stages every half clock cycle. from input to output the total latency is 8 clock cycles. each pipeline converter stage converts its input voltage to a digital output code. at every stage, except the last, the error between the input voltage and the digital out- put code is multiplied and passed along to the next pipeline stage. digital error correction compensates for adc comparator offsets in each pipeline stage and ensures no missing codes. figure 2 shows the MAX12527 functional diagram. dual, 65msps, 12-bit, if/baseband adc 14 ______________________________________________________________________________________ pin name function 66 shref shared reference digital input. shref = v dd : shared reference enabled. shref = gnd: shared reference disabled. when sharing the reference, externally connect refap and refbp together to ensure that v refap equals v refbp . similarly, when sharing the reference, externally connect refan to refbn together to ensure that v refan = v refbn . 67 refout internal reference voltage output. the refout output voltage is 2.048v and refout can deliver 1ma. for internal reference operation, connect refout directly to refin or use a resistive divider from refout to set the voltage at refin. bypass refout to gnd with a 0.1f capacitor. for external reference operation, refout is not required and must be bypassed to gnd with a 0.1f capacitor. 68 refin single-ended reference analog input. for internal reference and buffered external reference operation, apply a 0.7v to 2.3v dc reference voltage to refin. bypass refin to gnd with a 4.7f capacitor. within its specified operating voltage, refin has a >50m input impedance, and the differential reference voltage (v ref_p - v ref_n ) is generated from refin. for unbuffered external reference operation, connect refin to gnd. in this mode ref_p, ref_n, and com_ are high-impedance inputs that accept the external reference voltages. ?ep exposed paddle. ep is internally connected to gnd. externally connect ep to gnd to achieve specified dynamic performance. pin description (continued) MAX12527 + ? digital error correction flash adc x2 dac stage 2 in_p in_n stage 1 stage 9 stage 10 end of pipeline d0_ through d11_ figure 1. pipeline architecture?tage blocks
MAX12527 dual, 65msps, 12-bit, if/baseband adc ______________________________________________________________________________________ 15 inbp 12-bit pipeline adc digital error correction channel a reference system coma refan refap ov dd dav output drivers dora clock divider d ata format 12-bit pipeline adc digital error correction output drivers d ata format div2 div4 inbn d0b to d11b dorb channel b reference system comb refbn refbp inap inan clkp clkn duty-cycle equalizer clock clock power control and bias circuits pd v dd gnd clock refin internal reference generator refout shref diffclk/seclk d0a to d11a g/t MAX12527 figure 2. functional diagram
MAX12527 analog inputs and input track-and-hold (t/h) amplifier figure 3 displays a simplified functional diagram of the input t/h circuit. this input t/h circuit allows for high analog input frequencies of 175mhz and beyond and supports a v dd / 2 common-mode input voltage. the MAX12527 sampling clock controls the switched- capacitor input t/h architecture (figure 3) allowing the analog input signals to be stored as charge on the sampling capacitors. these switches are closed (track mode) when the sampling clock is high and open (hold mode) when the sampling clock is low (figure 4). the analog input signal source must be able to provide the dynamic currents necessary to charge and discharge the sampling capacitors. to avoid signal degradation, these capacitors must be charged to one-half lsb accuracy within one-half of a clock cycle. the analog input of the MAX12527 supports differential or single- ended input drive. for optimum performance with dif- ferential inputs, balance the input impedance of in_p and in_n and set the common-mode voltage to mid- supply (v dd / 2). the MAX12527 provides the optimum common-mode voltage of v dd / 2 through the com output when operating in internal reference mode and buffered external reference mode. this com output voltage can be used to bias the input network as shown in figures 9, 10, and 11. reference output an internal bandgap reference is the basis for all the internal voltages and bias currents used in the MAX12527. the power-down logic input (pd) enables and disables the reference circuit. refout has approxi- mately 17k to gnd when the MAX12527 is powered down. the reference circuit requires 10ms to power up and settle to its final value when power is applied to the MAX12527 or when pd transitions from high to low. the internal bandgap reference produces a buffered reference voltage of 2.048v 1% at the refout pin with a 50ppm/?c temperature coefficient. connect an external 0.1f bypass capacitor from refout to gnd for stability. refout sources up to 1ma and sinks up to 0.1ma for external circuits with a 35mv/ma load regulation. short-circuit protection limits i refout to a 2.1ma source current when shorted to gnd and a 0.24ma sink current when shorted to v dd . similar to refout, refin should be bypassed with a 4.7f capacitor to gnd. reference configurations the MAX12527 full-scale analog input range is 2/3 x v ref with a v dd / 2 0.5v common-mode input range. v ref is the voltage difference between refap (refbp) and refan (refbn). the MAX12527 provides three modes of reference operation. the voltage at refin (v refin ) selects the reference operation mode (table 1). connect refout to refin either with a direct short or through a resistive divider to enter internal reference mode. com_, ref_p, and ref_n are low-impedance outputs with v com_ = v dd / 2, v refp = v dd / 2 + 3/8 x v refin , and v ref_n = v dd / 2 - 3/8 x v refin . bypass ref_p, ref_n, and com_ each with a 0.1f capacitor to gnd. bypass ref_p to ref_n with a 10f capacitor. dual, 65msps, 12-bit, if/baseband adc 16 ______________________________________________________________________________________ v refin reference mode 35% v refout to 100% v refout internal reference mode. refin is driven by refout either through a direct short or a resistive divider. v com_ = v dd / 2 v ref_p = v dd / 2 + 3/8 x v refin v ref_n = v dd / 2 - 3/8 x v refin 0.7v to 2.3v buffered external reference mode. an external 0.7v to 2.3v reference voltage is applied to refin. v com_ = v dd / 2 v ref_p = v dd / 2 + 3/8 x v refin v ref_n = v dd / 2 - 3/8 x v refin <0.5v u nb uffer ed e xter nal refer ence m od e. re f_p , re f_n , and c o m _ ar e d r i ven b y exter nal r efer ence sour ces. the ful l - scal e anal og i np ut r ang e i s ( v r e f _p - v r e f _n ) x 2/ 3. table 1. reference modes MAX12527 c par 2pf v dd bond wire inductance 1.5nh in_p sampling clock *the effective resistance of the switched sampling capacitors is: *c sample 4.5pf c par 2pf v dd bond wire inductance 1.5nh in_n *c sample 4.5pf r in = 1 f clk x c sample figure 3. internal t/h circuit
bypass refin and refout to gnd with a 0.1f capac- itor. the refin input impedance is very large (>50m ). when driving refin through a resistive divider, use resistances 10k to avoid loading refout. buffered external reference mode is virtually identical to the internal reference mode except that the reference source is derived from an external reference and not the MAX12527?s internal bandgap reference. in buffered external reference mode, apply a stable reference volt- age source between 0.7v to 2.3v at refin. pins com_, ref_p, and ref_n are low-impedance outputs with v com_ = v dd / 2, v ref_p = v dd / 2 + 3/8 x v refin , and v ref_n = v dd / 2 - 3/8 x v refin . bypass ref_p, ref_n, and com_ each with a 0.1f capacitor to gnd. bypass ref_p to ref_n with a 10f capacitor. connect refin to gnd to enter unbuffered external ref- erence mode. connecting refin to gnd deactivates the on-chip reference buffers for com_, ref_p, and ref_n. with their buffers deactivated, com_, ref_p, and ref_n become high-impedance inputs and must be driven with separate, external reference sources. drive v com_ to v dd / 2 5%, and drive ref_p and ref_n so v com_ = (v ref_p_ + v ref_n_ ) / 2. the analog input range is (v ref_p_ - v ref_n ) x 2/3. bypass ref_p, ref_n, and com_ each with a 0.1f capacitor to gnd. bypass ref_p to ref_n with a 10f capacitor. for all reference modes, bypass refout with a 0.1f and refin with a 4.7f capacitor to gnd. the MAX12527 also features a shared reference mode, in which the user can achieve better channel-to-chan- nel matching. when sharing the reference (shref = v dd ), externally connect refap and refbp together to ensure that v refap = v refbp . similarly, when sharing the reference, externally connect refan to refbn together to ensure that v refan = v refbn . connect shref to gnd to disable the shared refer- ence mode of the MAX12527. in this independent refer- ence mode, a better channel-to-channel isolation is achieved. for detailed circuit suggestions and how to drive the adc in buffered/unbuffered external reference mode, see the applications information section. clock duty-cycle equalizer the MAX12527 has an internal clock duty-cycle equaliz- er, which makes the converter insensitive to the duty cycle of the signal applied to clkp and clkn. the con- verters allow clock duty-cycle variations from 25% to 75% without negatively impacting the dynamic performance. the clock duty-cycle equalizer uses a delay-locked loop (dll) to create internal timing signals that are duty-cycle independent. due to this dll, the MAX12527 requires approximately 100 clock cycles to acquire and lock to new clock frequencies. clock input and clock control lines the MAX12527 accepts both differential and single- ended clock inputs with a wide 25% to 75% input clock duty cycle. for single-ended clock input operation, connect diffclk/ seclk clk clk t clk seclk clk clk c clk clk l s t clk clk s c c s s c c t t t s c
MAX12527 sampling provides design flexibility, relaxes clock requirements, and can minimize clock jitter. system timing requirements figure 5 shows the timing relationship between the clock, analog inputs, dav indicator, dor_ indicators, and the resulting output data. the analog input is sam- pled on the falling (rising) edge of clkp (clkn) and the resulting data appears at the digital outputs 8 clock cycles later. the dav indicator is synchronized with the digital out- put and optimized for use in latching data into digital back-end circuitry. alternatively, digital back-end cir- cuitry can be latched with the rising edge of the con- version clock (clkp - clkn). data-valid output dav is a single-ended version of the input clock that is compensated to correct for any input clock duty-cycle variations. the MAX12527 output data changes on the falling edge of dav, and dav rises once the output data is valid. the falling edge of dav is synchronized to have a 5.4ns delay from the falling edge of the input clock. output data at d0a/bed11a/b and dora/b are valid from 7ns before the rising edge of dav to 7ns after the rising edge of dav. dav enters high impedance when the MAX12527 is powered down (pd = ov dd ). dav enters its high- impedance state 10ns after the rising edge of pd and becomes active again 10ns after pd transitions low. dav is capable of sinking and sourcing 600a and has three times the driving capabilities of d0a/bed11a/b and dora/b. dav is typically used to latch the MAX12527 output data into an external digital back-end circuit. keep the capacitive load on dav as low as possi- ble (<15pf) to avoid large digital currents feeding back into the analog portion of the MAX12527, thereby degrading its dynamic performance. buffering dav dual, 65msps, 12-bit, if/baseband adc 18 ______________________________________________________________________________________ MAX12527 clkp clkn v dd gnd 10k 10k 10k 10k duty-cycle equalizer s 1h s 2h s 2l s 1l switches s 1_ and s 2_ are open during power-down making clkp and clkn high impedance. switches s 2_ are open in single-ended clock mode. figure 4. siimplified clock input circuit div4 div2 function 00 clock divider disabled f sample = f clk 01 divide-by-two clock divider f sample = f clk / 2 10 divide-by-four clock divider f sample = f clk / 4 11 not allowed table 2. clock-divider control inputs dav n n + 1 n +2 n + 3 n + 4 n + 5 n + 6 n + 7 n + 8 n + 9 t dav t setup t ad n - 1 n - 2 n - 3 t hold t cl t ch differential analog input (in_p?n_n) clkn clkp (v ref_p - v ref_n ) x 2/3 (v ref_n - v ref_p ) x 2/3 n + 4 d0_?11_ dor 8.0 clock-cycle data latency t setup t hold nn + 1 n + 2 n + 3 n + 5 n + 6 n + 7 n - 1 n - 2 n - 3 n + 9 n + 8 figure 5. system timing diagram
externally isolates it from heavy capacitive loads. refer to the MAX12527 ev kit schematic for recommendations of how to drive the dav signal through an external buffer. data out-of-range indicator the dora and dorb digital outputs indicate when the analog input voltage is out of range. when dor_ is high, the analog input is out of range. when dor_ is low, the analog input is within range. the valid differential input range is from (v ref_p - v ref_n ) x 2/3 to (v ref_n - v ref_p ) x 2/3. signals outside of this valid differential range cause dor_ to assert high as shown in table 1. dor is synchronized with dav and transitions along with the output data d11?0. there is an 8 clock-cycle latency in the dor function as is with the output data (figure 5). dor_ is high impedance when the MAX12527 is in power-down (pd = high). dor_ enters a high-impedance state within 10ns after the rising edge of pd and becomes active 10ns after pd? falling edge. digital output data and output format selection the MAX12527 provides two 12-bit, parallel, tri-state output buses. d0a/b?11a/b and dora/b update on the falling edge of dav and are valid on the rising edge of dav. the MAX12527 output data format is either gray code or two? complement depending on the logic input g/ t t t s t t c t e e ce t c t e e ce ce t MAX12527 dual, 65msps, 12-bit, if/baseband adc ______________________________________________________________________________________ 19 gray-code output code (g/ t = 1) two? complement output code (g/ t = 0) binary d11a?0a d11b?0b dor h exa d ecim a l equivalent of d11a?0a d11b?0b decimal equivalent of d11a?0a d11b?0b (code 10 ) binary d11a?0a d11b?0b dor hexadecimal equivalent of d11a?0a d11b?0b decimal equivalent of d11a?0a d11b?0b (code 10 ) v in_p - v in_n v ref_p = 2.418v v ref_n = 0.882v 1000 0000 0000 1 0x800 +4095 0111 1111 1111 1 0x7ff +2047 >+1.0235v (data out of range) 1000 0000 0000 0 0x800 +4095 0111 1111 1111 0 0x7ff +2047 +1.0235v 1000 0000 0001 0 0x801 +4094 0111 1111 1110 0 0x7fe +2046 +1.0230v 1100 0000 0011 0 0xc03 +2050 0000 0000 0010 0 0x002 +2 +0.0010v 1100 0000 0001 0 0xc01 +2049 0000 0000 0001 0 0x001 +1 +0.0005v 1100 0000 0000 0 0xc00 +2048 0000 0000 0000 0 0x000 0 +0.0000v 0100 0000 0000 0 0x400 +2047 1111 1111 1111 0 0xfff -1 -0.0005v 0100 0000 0001 0 0x401 +2046 1111 1111 1110 0 0xffe -2 -0.0010v 0000 0000 0001 0 0x001 +1 1000 0000 0001 0 0x801 -2047 -1.0235v 0000 0000 0000 0 0x000 0 1000 0000 0000 0 0x800 -2048 -1.0240v 0000 0000 0000 1 0x000 0 1000 0000 0000 1 0x800 -2048 <-1.0240v (data out of range) table 3. output codes vs. input voltage
MAX12527 the digital outputs d0a/bed11a/b are high impedance when the MAX12527 is in power-down (pd = 1) mode. d0a/bed11a/b enter this state 10ns after the rising edge of pd and become active again 10ns after pd transitions low. keep the capacitive load on the MAX12527 digital out- puts d0a/bed11a/b as low as possible (<15pf) to avoid large digital currents feeding back into the ana- log portion of the MAX12527 and degrading its dynam- ic performance. adding external digital buffers on the digital outputs helps isolate the MAX12527 from heavy capacitive loads. to improve the dynamic performance of the MAX12527, add 220 resistors in series with the digital outputs close to the MAX12527. see the max12557 ev kit schematic for guidelines of how to drive the digital outputs through 220 series resistors and external digital output buffers. power-down input the MAX12527 has two power modes that are con- trolled with a power-down digital input (pd). with pd low, the MAX12527 is in its normal operating mode. with pd high, the MAX12527 is in power-down mode. the power-down mode allows the MAX12527 to effi- ciently use power by transitioning to a low-power state when conversions are not required. additionally, the MAX12527 parallel output bus goes high-impedance in power-down mode, allowing other devices on the bus to be accessed. in power-down mode all internal circuits are off, the analog supply current reduces to less than 50a, and the digital supply current reduces to 1a. the following list shows the state of the analog inputs and digital out- puts in power-down mode. 1) inap/b, inan/b analog inputs are disconnected from the internal input amplifier (figure 3). 2) refout has approximately 17k to gnd. 3) refap/b, coma/b, refan/b enter a high-imped- ance state with respect to v dd and gnd, but there is an internal 4k resistor between refap/b and coma/b as well as an internal 4k resistor between refan/b and coma/b. 4) d0aed11a, d0bed11b, dora, and dorb enter a high-impedance state. 5) dav enters a high-impedance state. 6) clkp, clkn clock inputs enter a high-impedance state (figure 4). the wake-up time from power-down mode is dominated by the time required to charge the capacitors at ref_p, ref_n, and com. in internal reference mode and buffered external reference mode the wake-up time is typically 10ms. when operating in the unbuffered exter- nal reference mode the wake-up time is dependent on the external reference drivers. dual, 65msps, 12-bit, if/baseband adc 20 ______________________________________________________________________________________ differential input voltage (lsb) two's-complement output code (lsb) -2045 +2047 +2045 -1 0 +1 -2047 0x800 0x801 0x802 0x803 0x7ff 0x7fe 0x7fd 0xfff 0x000 0x001 2/3 x (v refp - v refn ) 2/3 x (v refp - v refn ) 1 lsb = 4/3 x (v refp - v refn ) / 4096 figure 6. two?-complement transfer function (g/ t differential input voltage (lsb) gray output code (lsb) -2045 +2047 +2045 -1 0 +1 -2047 0x000 0x001 0x003 0x002 0x800 0x801 0x803 0xc00 0xc00 0xc01 2/3 x (v refp - v refn ) 2/3 x (v refp - v refn ) 1 lsb = 4/3 x (v refp - v refn ) / 4096 figure 7. gray-code transfer function (g/ t
MAX12527 dual, 65msps, 12-bit, if/baseband adc ______________________________________________________________________________________ 21 binary-to-gray code conversion 1) the most significant gray-code bit is the same as the most significant binary bit. 0111 0100 1100 binary gray code 0 2) subsequent gray-code bits are found according to the following equation: d11 d7 d3 d0 gray x = binary x + binary x + 1 bit position 01 11 0100 1100 binary gray code 0 d11 d7 d3 d0 bit position gray 10 = binary 10 binary 11 gray 10 = 1 0 gray 10 = 1 1 3) repeat step 2 until complete: 01 11 0100 1100 binary gray code 0 d11 d7 d3 d0 bit position gray 9 = binary 9 binary 10 gray 9 = 1 1 gray 9 = 0 10 4) the final gray-code conversion is: 0111 0100 1100 binary gray code 0 d11 d7 d3 d0 bit position 100 1 10 1 1010 gray-to-binary code conversion 1) the most significant binary bit is the same as the most significant gray-code bit. 2) subsequent binary bits are found according to the following equation: d11 d7 d3 d0 binary x = binary x+1 bit position binary 10 = binary 11 gray 10 binary 10 = 0 1 binary 10 = 1 3) repeat step 2 until complete: 4) the final binary conversion is: 0100 1110 1010 binary gray code d11 d7 d3 d0 bit position 0 binary gray code 0100 11 0 11010 binary 9 = binary 10 gray 9 binary 9 = 1 0 binary 9 = 1 gray x 0100 1110 1010 binary gray code 0 d11 d7 d3 d0 bit position 1 01 00 1110 1010 binary gray code 0 d11 d7 d3 d0 bit position 11 0111 0100 1100 ab y=ab 00 01 10 11 0 1 1 0 exclusive or truth table where is the exclusive or function (see truth t able below) and x is the bit position: + where is the exclusive or function (see truth t able below) and x is the bit position: + + + + + + + + + + + + + + + figure 8 shows the gray-to-binary and binary-to-gray code conversion in offset binary format. the output format of the MAX12527 is two's-complement binary, hence each msb of the two's-complement output code must be inserted to reflect true offset binary format. figure 8. binary-to-gray and gray-to-binary code conversion
MAX12527 applications information using transformer coupling in general, the MAX12527 provides better sfdr and thd with fully differential input signals than single- ended input drive, especially for input frequencies above 125mhz. in differential input mode, even-order harmonics are lower as both inputs are balanced, and each of the adc inputs only requires half the signal swing compared to single-ended input mode. an rf transformer (figure 9) provides an excellent solution to convert a single-ended input source signal to a fully differential signal, required by the MAX12527 for optimum performance. connecting the center tap of the transformer to com provides a v dd / 2 dc level shift to the input. although a 1:1 transformer is shown, a step-up transformer can be selected to reduce the drive requirements. a reduced signal swing from the input driver, such as an op amp, can also improve the overall distortion. the configuration of figure 9 is good for frequencies up to nyquist (f clk / 2). the circuit of figure 10 converts a single-ended input signal to fully differential just as figure 9. however, figure 10 utilizes an additional transformer to improve the common-mode rejection allowing high-frequency signals beyond the nyquist frequency. a set of 75 and 113 termination resistors provide an equivalent 50 termination to the signal source. the second set of termination resistors connects to com_ providing the correct input common-mode voltage. two 0 resistors in series with the analog inputs allow high if input fre- quencies. these 0 resistors can be replaced with low- value resistors to limit the input bandwidth. single-ended ac-coupled input signal figure 11 shows an ac-coupled, single-ended input application. the max4108 provides high speed, high bandwidth, low noise, and low distortion to maintain the input signal integrity. dual, 65msps, 12-bit, if/baseband adc 22 ______________________________________________________________________________________ MAX12527 1 5 3 6 2 4 n.c. v in 0.1 f t1 minicircuits tt1-6 or t1-1t 24.9 24.9 5.6pf 5.6pf 0.1 f in_p com_ in_n figure 9. transformer-coupled input drive for input frequencies up to nyquist 1 5 3 6 2 4 n.c. v in 0.1 f t1 minicircuits adt1-1wt 5.6pf 5.6pf in_p com_ in_n *0 resistors can be replaced with low-value resistors to limit the input bandwidth. n.c. 1 5 3 6 2 4 n.c. t2 minicircuits adt1-1wt n.c. 75 1% 75 1% 113 0.5% 113 0.5% 0.1 f 0 * 0 * MAX12527 figure 10. transformer-coupled input drive for input frequencies beyond nyquist MAX12527 max4108 0.1 f 0.1 f 0 5.6pf in_p com_ in_n 100 100 v in 24.9 24.9 5.6pf figure 11. single-ended, ac-coupled input drive
buffered external reference drives multiple adcs the buffered external reference mode allows for more control over the MAX12527 reference voltage and allows multiple converters to use a common reference. the refin input impedance is >50m ? . figure 12 shows the max6029 precision 2.048v bandgap reference used as a common reference for multiple con- verters. the 2.048v output of the max6029 passes through a single-pole 10hz lp filter to the max4230. the max4230 buffers the 2.048v reference and pro- vides additional 10hz lp filtering before its output is applied to the refin input of the MAX12527. unbuffered external reference drives multiple adcs the unbuffered external reference mode allows for pre- cise control over the MAX12527 reference and allows multiple converters to use a common reference. connecting refin to gnd disables the internal refer- MAX12527 dual, 65msps, 12-bit, if/baseband adc ______________________________________________________________________________________ 23 max4230 0.1 f 1 f 5 2 3 4 1 1 5 2 refin v dd gnd 0.1 f 47 ? 3.3v 2.048v 16.2k ? refout 0.1 f ref_p ref_n com_ 0.1 f 0.1 f 0.1 f 2.2 f 0.1 f 3.3v 1.47k ? 300 f 6v note: one front-end reference circuit is capable of sourcing up to 15ma and sinking up to 30ma of output current. 10 f 0.1 f refin v dd gnd refout 0.1 f ref_p ref_n com_ 0.1 f 0.1 f 0.1 f 2.2 f 0.1 f 10 f 0.1 f MAX12527 max6029 (euk21) MAX12527 figure 12. external buffered (max4230) reference drive using a max6029 bandgap reference
MAX12527 ence, allowing ref_p, ref_n, and com_ to be driven directly by a set of external reference sources. figure 13 uses a max6029 precision 3.000v bandgap reference as a common reference for multiple convert- ers. a seven-component resistive divider chain follows the max6029 voltage reference. the 0.47f capacitor along this chain creates a 10hz lp filter. three max4230 amplifiers buffer taps along this resistor chain providing 2.413v, 1.647v, and 0.880v to the MAX12527 ref_p, ref_n, and com_ reference inputs. the feedback around the max4230 op amps provides additional 10hz lp filtering. reference volt- ages 2.413v and 0.880v set the full-scale analog input range for the converter to 1.022v ([v ref_p - v ref_n ] x 2/3). note that one single power supply for all active circuit components removes any concern regarding power- supply sequencing when powering up or down. grounding, bypassing, and board layout the MAX12527 requires high-speed board layout design techniques. refer to the max12557 ev kit data sheet for a board layout reference. locate all bypass capacitors as close to the device as possible, prefer- ably on the same side as the adc, using surface- dual, 65msps, 12-bit, if/baseband adc 24 ______________________________________________________________________________________ MAX12527 max4230 max6029 (euk30) 0.1 f 1 5 2 0.47 f 10 f 6v 47 1.47k 2.413v 3v 4 1 3 330 f 6v max4230 10 f 6v 47 1.47k 1.647v 4 1 3 330 f 6v max4230 10 f 6v 47 1.47k 0.880v 4 1 3 330 f 6v ref_p ref_n com_ v dd gnd refin 3.3v 3.3v refout 0.1 f 0.1 f 0.1 f 10 f 0.1 f 2.2 f 0.1 f 20k 1% 20k 1% 20k 1% 20k 1% 20k 1% 52.3k 1% 52.3k 1% 0.1 f MAX12527 ref_p ref_n com_ v dd gnd refin refout 0.1 f 0.1 f 0.1 f 10 f 0.1 f 2.2 f 0.1 f 0.1 f figure 13. external unbuffered reference driving multiple adcs
mount devices for minimum inductance. bypass v dd to gnd with a 220f ceramic capacitor in parallel with at least one 10f, one 4.7f, and one 0.1f ceramic capacitor. bypass ov dd to gnd with a 220f ceramic capacitor in parallel with at least one 10f, one 4.7f, and one 0.1f ceramic capacitor. high-frequency bypassing/decoupling capacitors should be located as close as possible to the converter supply pins. multilayer boards with ample ground and power planes produce the highest level of signal integrity. all grounds and the exposed backside paddle of the MAX12527 must be connected to the same ground plane. the MAX12527 relies on the exposed backside paddle con- nection for a low-inductance ground connection. isolate the ground plane from any noisy digital system ground planes such as a dsp or output buffer ground. route high-speed digital signal traces away from the sensitive analog traces. keep all signal lines short and free of 90 turns. ensure that the differential, analog input network layout is symmetric and that all parasitic components are bal- anced equally. refer to the max12557 ev kit data sheet for an example of symmetric input layout. parameter definitions integral nonlinearity (inl) inl is the deviation of the values on an actual transfer function from a straight line. for the MAX12527, this straight line is between the endpoints of the transfer function, once offset and gain errors have been nulli- fied. inl deviations are measured at every step of the transfer function and the worst-case deviation is report- ed in the electrical characteristics table. differential nonlinearity (dnl) dnl is the difference between an actual step width and the ideal value of 1 lsb. a dnl error specification of less than 1 lsb guarantees no missing codes and a monotonic transfer function. for the MAX12527, dnl deviations are measured at every step of the transfer function and the worst-case deviation is reported in the electrical characteristics table. offset error offset error is a figure of merit that indicates how well the actual transfer function matches the ideal transfer function at a single point. ideally, the midscale MAX12527 transition occurs at 0.5 lsb above mid- scale. the offset error is the amount of deviation between the measured midscale transition point and the ideal midscale transition point. gain error gain error is a figure of merit that indicates how well the slope of the actual transfer function matches the slope of the ideal transfer function. the slope of the actual trans- fer function is measured between two data points: posi- tive full scale and negative full scale. ideally, the positive full-scale MAX12527 transition occurs at 1.5 lsbs below positive full scale, and the negative full-scale transition occurs at 0.5 lsb above negative full scale. the gain error is the difference of the measured transition points minus the difference of the ideal transition points. small-signal noise floor (ssnf) ssnf is the integrated noise and distortion power in the nyquist band for small-signal inputs. the dc offset is excluded from this noise calculation. for this converter, a small signal is defined as a single tone with an ampli- tude of -35dbfs. this parameter captures the thermal and quantization noise characteristics of the data con- verter and can be used to help calculate the overall noise figure of a digital receiver signal path. signal-to-noise ratio (snr) for a waveform perfectly reconstructed from digital samples, the theoretical maximum snr is the ratio of the full-scale analog input (rms value) to the rms quantization error (residual error). the ideal, theoretical minimum analog-to-digital noise is caused by quantiza- tion error only and results directly from the adc?s reso- lution (n bits): snr [max] = 6.02 n + 1.76 in reality, there are other noise sources besides quanti- zation noise: thermal noise, reference noise, clock jitter, etc. snr is computed by taking the ratio of the rms signal to the rms noise. rms noise includes all spec- tral components to the nyquist frequency excluding the fundamental, the first six harmonics (hd2 through hd7), and the dc offset. snr = 20 x log (signal rms / noise rms ) signal-to-noise plus distortion (sinad) sinad is computed by taking the ratio of the rms sig- nal to the rms noise plus distortion. rms noise plus distortion includes all spectral components to the nyquist frequency excluding the fundamental and the dc offset. MAX12527 dual, 65msps, 12-bit, if/baseband adc ______________________________________________________________________________________ 25
MAX12527 total harmonic distortion (thd) thd is the ratio of the rms sum of the first six harmon- ics of the input signal to the fundamental itself. this is expressed as: where v 1 is the fundamental amplitude, and v 2 through v 7 are the amplitudes of the 2nd- through 7th-order harmonics (hd2 through hd7). spurious-free dynamic range (sfdr) sfdr is the ratio expressed in decibels of the rms amplitude of the fundamental (maximum signal compo- nent) to the rms value of the next largest spurious component, excluding dc offset. intermodulation distortion (imd) imd is the total power of the im2 to im5 intermodulation products to the nyquist frequency relative to the total input power of the two input tones f in1 and f in2 . the individual input tone levels are at -7dbfs. the inter- modulation products are as follows: 2nd-order intermodulation products (im2): f in1 = f in2 , f in2 - f in1 3rd-order intermodulation products (im3): 2 x f in1 - f in2 , 2 x f in2 - f in1 , 2 x f in1 + f in2 , 2 x f in2 + f in1 4th-order intermodulation products (im4): 3 x f in1 - f in2 , 3 x f in2 - f in1 , 3 x f in1 + f in2 , 3 x f in2 + f in1 , 2 x f in1 - 2 x f in2 , 2 x f in1 + 2 x f in2 , 2 x f in2 - 2 x f in1 5th-order intermodulation products (im5): 3 x f in1 - 2 x f in2 , 3 x f in2 - 2 x f in1 , 3 x f in1 + 2 x f in2 , 3 x f in2 + 2 x f in1 , 4 x f in1 - f in2 , 4 x f in2 - f in1 , 4 x f in1 + f in2 , 4 x f in2 + f in1 note that the two-tone intermodulation distortion is mea- sured with respect to a single-carrier amplitude and not the peak-to-average input power of both input tones. 3rd-order intermodulation (im3) im3 is the total power of the 3rd-order intermodulation product to the nyquist frequency relative to the total input power of the two input tones f in1 and f in2 . the individual input tone levels are at -7dbfs. the 3rd- order intermodulation products are 2 x f in1 - f in2 , 2 x f in2 - f in1 , 2 x f in1 + f in2 , 2 x f in2 + f in1 . aperture jitter figure 14 shows the aperture jitter (t aj ), which is the sample-to-sample variation in the aperture delay. aperture delay aperture delay (t ad ) is the time defined between the rising edge of the sampling clock and the instant when an actual sample is taken (figure 14). full-power bandwidth a large -0.2dbfs analog input signal is applied to an adc and the input frequency is swept up to the point where the amplitude of the digitized conversion result has decreased by -3db. this point is defined as full- power input bandwidth frequency. output noise (n out ) the output noise (n out ) parameter is similar to thermal plus quantization noise and is an indication of the con- verter?s overall noise performance. no fundamental input tone is used to test for n out . in_p, in_n, and com_ are connected together and 1024k data points are collected. n out is computed by taking the rms value of the collected data points after the mean is removed. overdrive recovery time overdrive recovery time is the time required for the adc to recover from an input transient that exceeds the full-scale limits. the MAX12527 specifies overdrive recovery time using an input transient that exceeds the full-scale limits by 10%. the MAX12527 requires one clock cycle to recover from the overdrive condition. crosstalk coupling onto one channel being driven by a (-0.5dbfs) signal when the adjacent interfering channel is driven by a full-scale signal. measurement includes all spurs resulting from both direct coupling and mixing components. thd vvvvvv v log = +++++

20 2 2 3 2 4 2 5 2 6 2 7 2 1 dual, 65msps, 12-bit, if/baseband adc 26 ______________________________________________________________________________________ t ad t aj t/h track hold hold clkn clkp analog input sampled d ata figure 14. t/h aperture timing
gain matching gain matching is a figure of merit that indicates how well the gains between the two channels are matched to each other. the same input signal is applied to both channels and the maximum deviation in gain is report- ed (typically in db) as gain matching. offset matching like gain matching, offset matching is a figure of merit that indicates how well the offsets between the two chan- nels are matched to each other. the same input signal is applied to both channels and the maximum deviation in offset is reported (typically in %fsr) as offset matching. MAX12527 dual, 65msps, 12-bit, if/baseband adc ______________________________________________________________________________________ 27 58 59 60 61 62 54 55 56 57 63 38 39 40 41 42 43 44 45 46 47 refbp clkn v dd thin qfn top view v dd v dd ov dd dora d11a d10a d9a d8a d7a 52 53 d6a d5a div2 clkp v dd div4 v dd v dd ov dd v dd n.c. n.c. d1b d0b d2b d0a n.c. n.c. dav ov dd dorb d11b d10b d9b d8b 35 36 37 d7b d6b d5b exposed paddle (gnd) refbn gnd refan refap coma inbp inbn gnd gnd comb gnd gnd inan inap 48 d1a gnd 64 g/t 65 66 67 refout shref pd 68 refin 23 22 21 20 19 27 26 25 24 18 29 28 32 31 30 d3b d4b 34 33 49 50 d3a d2a 51 d4a 11 10 9 8 7 6 5 4 3 2 16 15 14 13 12 1 gnd 17 MAX12527 diffclk/seclk pin configuration
MAX12527 dual, 65msps, 12-bit, if/baseband adc maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a maxim product. no circu it patent licenses are implied. maxim reserves the right to change the circuitry and specifications without notice at any time. 28 ____________________maxim integrated products, 120 san gabriel drive, sunnyvale, ca 94086 408-737-7600 ? 2005 maxim integrated products printed usa is a registered trademark of maxim integrated products, inc. package information (the package drawing(s) in this data sheet may not reflect the most current specifications. for the latest package outline info rmation, go to www.maxim-ic.com/packages .) 68l qfn thin.eps c 1 2 21-0142 package outline 68l thin qfn, 10x10x0.8mm c 2 2 21-0142 package outline 68l thin qfn, 10x10x0.8mm

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